Isolated Power Supply world-wide AC input

Part 4

Measuring Output with more Precision

Mesuring now AC rms voltage with a true rms DMM, before was measuring with the transformer neddle meter, not enough precision. When applying low 90 VAC rms under full load, supply switch OFF. Therefore increasing current limit by a shunt resistor change.

Figure 57
Shunt changed, now 20.7W load runs under 100VAC rms, with a lower voltage Supply switch OFF. Lowest supply voltage requires the most current in the primary winding. Core has reached maximum power, core become into saturation, current rise very fast for high currents - core can not store more magnetic energy. Further increasing current can damage the circuit.

Core becomes warm when supplied with 1.4A peak. Maximum load must be decreased for a save core.

Reducing load to 16.3 Watt:
minimum possible AC voltage = 85VAC rms @ 25°C, 16.3 Watt, 28VDC

Figure 58
Load decreased to 16.3Watt, minimum 85VAC rms can be reached. Core close in saturation. Consider this is room temperature, an additional ambient temperature weaks the possible core saturation. Output voltage adjusted close as possible to 28.0VDC.

033 Figure 59
Core saturates when input sine wave reach its higher voltage. Controller peak current detection approximately adjusted to 1,4A.
It is possible to increase the peak current limit, but the rising current slope will increase further. Only the current will increase, but not the area under the current, the integral indicates stored magnetic energy - Increasing current, a good idea when integral can be increased, but when doing here only increasing current slope resulting in losses in core and MOSFET.

Figure 60
The current probe can not be recognized by the oscilloscope, different manufactorer, scale in volt/div.

Channel 1 * Channel 2 = Channel A (Power)

1V * 0.01V = 0.01V² == 0.5W      ==>    1V²== 50W

When switching OFF the MOSFET there is a switching peak power of 10V² ==  500Wpeak

Figure 61
Same measurement as Fig. 60, faster timebase. MOSFET peak power 500W for approx. 100ns.
Energy: 500W*100ns = 50µ Joule (but more than 100000 times per second). This is an important parameter in the absolute maximum ratings, the used MOSFET has a 140µJ limit. If the designer decides to decrease the switching speed for a better EMC, keep the "Avalanche energy, repetitive" in consideration, I am not sure if this parameter is valid for both current directions, I think so.

This measurement require good quality and fast probing. A fast scope with high sample rate an advantage. Would be an excellent task for a fast, high sample rate scope - some models with special power software options available.  Ideal for a fast >8bit resolution model.

Consider also, a fast 500Wpk can be a good and powerfull EMC source, when connecting to an well adapted arial - highest emission. Therefore it is a number-one-task in the layout for the Drain net, to create a "most bad adapted arial", keep most of the energy in the wires and prevent from radiating as electromagnetic wave.

Drain voltage and Drain current are in 90° phase shift - LC oscillator.

Figure 62
a lower load, looks perfect.

Figure 63
An electronic load with inrush current. Controller detects high inrush currents for a Switch-OFF.

Further Increasing the Current Peak limit

Figure 64
For a test purpose current peak limit has been increased from 1.4Apk to 1.7Apk. Core comes into more saturation. Not much gain on more magnetic stored energy, but highly increasing useless extra currents through the MOSFET, resulting in extra heat of core, winding and MOSFET - this is too much core saturation.

Figure 65
Measuring a maximum powered MOSFET. Current integrated in the area with the most current. Controller Ipk level still set to 1.7Apk (saturation started).

rms value (both current directions, MOSFET+Diode) = 10.59mV = 530mA rms

MOSFET slew-rate

Figure 66
Running circuit under 230VAC rms. Measuring the risetime of the Drain voltage when switching OFF.

Scope set to a 20% to 80% risetime measurement, this means in Figure 66, the risetime mesured between 120V-480V. Deltavoltage 480V-120V=360V

Slew-rate = 360V/86ns = 4.2V/ns, Datasheet absolute maximum rating: max. 50V/ns.

Figure 67

Slew-rate here 4.6V/ns

Measuring Output Diode with more Precision

Figure 68
Channel A (dark blue): Output diode voltage
Channel B (red): Output diode current
Channel A*B (light blue): Output diode power

@115VAC rms, 16.3Wout, 28VDC

True RMS Ch. B (current) = 1.945A rms for a cycle. Diode has 3A maximum average forward current limit. The 1.945A rms is a trustful value. Using here a 12Bit/200MHz oscilloscope, measures with more precision. Diode signals having a large dynamic range, from zero to high. Still a problem are any offset voltage caused by 50MHz current probe and voltage channel offset. The power calculation A*B, do not trust the values for highest precision, it is a good approximation, not more.

Beware when using such special equipment:

The risk using this 12bit scope, this type has only a specified max. +/-20 Volt input range, danger when working on a higher voltage power supply here. I don´t know at which voltage the input damages, not interested to know. Therefore using this scope only with a quality 1:100 probe, isolated current probe and doing only measurements had done before with another safer input scope. Necessary to think ALWAYS! at which potential the personal computer USB-ground actual connected.

Never use such special equipment for starting evaluation under higher voltage circuits. Use them only after knowing exactly the magnitude of signals.
  • new circuit
  • unknown signal
  • unknown circuit functions
  • handicaped by PC computer operation
Too many stress factors at the same time for a human being.

Measuring True rms Output diode voltage

Figure 69
Channel A (dark blue): Output diode voltage
Channel B (red): Output diode current
Channel A*B (light blue): Output diode power

@258VAC rms, 16.3Wout, 28VDC

Diode rms 1 cycle = 55.4V rms
Diode max. = 125.9V
Diode current rms = 2.1A rms

At high input voltage:
output diode voltage reach a maximum
frequency rise
Diode peak current decrease.
Diode rms cycle current increase.

Measuring MOSFET Reverse Diode fast voltage rise

Figure 70
Channel A (dark blue): MOSFET Drain-Source voltage
Channel B (red): Primary winding current (Drain + parallel C-resonant-Capacitor). The real Drain current can not be measured, because parallel there is a 220pF Resonant Capacitor. For a real Drain current measurement, Evaluation Board should be prepared with a Drain wire-loop.

@86VAC rms, 16.3Wout, 28VDC out

Here the MOSFET diode becomes very fast conducting during MOSFET Switch-OFF.

The recovery diode slope is the same falling and rising. The Flyback principle here use an unclamped inductive switching method resulting in fast voltage rise. Real drain current can not be seen, because of parallel Capacitor.

Danger under a too fast voltage rise:
internal parasitic Bipolar-Junction-Transistor can start conducting. In case of error, MOSFET becomes in ON-condition without applied gate voltage.

Not yet understood here for me, needs further measurements.

Measured Slew-rate under forward conducting body diode = -10.27V/5.2ns = -1.975V/ns

Please consider here also the bandwidth of the Test Equipment:
  • oscilloscope with 200MHz bandwidth, 12Bit oscilloscope
  • a 200MHz bandwidth scope has a typical rise/fall-time of 1.5ns to 2ns when using a quality passive probe tip.
  • 1:100 passive voltage probe
  • 50MHz current probe
  • unknown effects caused by parasitic u=L*di/dt in switching copper wires of the layout
  • additional galvanic + L*di/dt voltage drop caused by the serial Drain shunt resistor (<0.5ohm)
  • probe connection to the circuit has to be optimized with short lowest inductive leads
Measured 1.975V/ns, when using this 200MHz bandwidth scope may be a faster 3V/ns with ideal equipment. 
A verification requires  a faster oscilloscope and excellent probing. A good idea would be the use of a 500MHz or 1GHz scope together with a high quality 500MHz 1:10 or 1:100 passive probe. But it is a dangerous measurement for fast test equipment.
  • Fast probe has to widthstand the high 450Vpk (general faster probe means: smaller, more danger with high voltage)
  • Probe derating over frequency has to be considered, it will lower the capability of the max. allowed probe voltage.
  • High Bandwidth Scope having in general a lower maximum input voltage, CONSIDER => tears when destroyed.
  • 50 ohm technology can not be used => destroyed.
  • Fast Differential having in general a much lower max. input => destroyed.
  • Fast High Voltage Differential Probe could be an option, but consider requires some hundred MHz bandwidth, I don´t know an actual type.
For the person wants to know the exact slew-rate value, a demanding measurement and trigger task.

A fast Switching MOSFET is fine for a good power efficiency and space requirement, but has disadvantages in part reliability, part lifetime and EMC emmisions. Fast switching creates dv/dt stress on the MOSFET - not only heat cause stress on a MOSFET.

Measuring MOSFET Reverse Diode fast voltage rise

Figure 71

Current probe (primary coil) reversed.
  • Positive currents for a conducting MOSFET body diode (Source to Drain).
  • Negative currents (Drain to Source)
  • Triggered to a Drain Source voltage below Zero ==> Body diode conducting
Current probe has a specified typ. risetime of 7ns, cause an delay of the current waveform.
  • Controller switch-OFF the MOSFET very fast
  • stop charging core with more magnetic energy
  • primary coil current change direction, magnetic energy starts transfer to secondary side
  • body diode starts conducting under diode reverse recovery time
  • primary coil current change direction again under diode reverse recovery time
  • Drain voltage rise up fast with approx. 10V/40ns
Fastest Current slew-rate: approx. 1A/10ns (100A/µs), datasheet max. (400A/µs)
Fastest Voltage slew-rate under reverse recovery: approx. 10V/40ns

The oscilloscope should be faster for this measurement, 100MS/s single shot sample rate is not enough. But not a problem the quality can be observed.

Problem with too fast du/dt ratings, internal parasitic BJT can become in an unwanted conducting condition, not observed here.

Reading of MOSFET manufactorer application notes for explanation of max. du/dt and di/dt ratings required, measurement not yet fully understood for me.

Conclusion of Part 4

Core saturation: keep available maximum output power low as necessary.
Core saturation: depends on position within the input sine wave, search for the peak current.
Core saturation: adjust maximum peak current @ lowest input voltage and @ highest ambient temperatue.
Core saturation: Controller operating frequency too low, max. core power specified under higher frequency.
Core saturation: Controller frequency can not increased, no setting possible.
Flyback: unclamped inductive switching (clamped at higher peaks by TVS-diodes).
Flyback: cause high voltage V-drain-source stress.
Flyback: low part count
Controller: fast MOSFET Switch-OFF, reduce MOSFET switching losses
Controller: fast MOSFET Switch-OFF, cause dv/dt and di/dt MOSFET stress.
Controller: optimized for lowest part count, solution for PFC+DC/DC with one switching element only.
Controller: optimized for lowest MOSFET thermal losses
Controller: not optimized for EMC
Controller: not optimized for highest part reliability ==> MOSFET and Transformer must be careful choosen ==> OK
Controller: optimized for excellent starting and operating mode
Controller: optimized to handle successful error condition
Controller: control peak current for each cycle
Controller: Controller works perfect

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